2000 Fairchild Semiconductor International
www.fairchildsemi.com
Rev. 5.0
Features
Internal Startup Timer
Internal R/C filter which eliminates the Need for an
External R/C filter
Overvoltage Comparator eliminates Runaway Output
Voltage
Zero Current Detector
One Quadrant Multiplier
Trimmed 1.5% Internal Bandgap Reference
Under Voltage Lock Out with 5V of Hysteresis
Totem Pole Output with High State Clamp
Low Startup and Operating Current
8-Pin DIP or 8-Pin SOP
Applications
Electronic Ballast
SMPS
Descriptions
The KA7526 provides simple and high performance active
power factor correction. KA7526 is optimized for electronic
ballast and low power, high density power supplies requiring
a minimum board area, reduced component count and low
power dissipation. Addition of internal R/C filter eliminates
the need for an external R/C filter. Internal clamping of the
error amplifier and multiplier outputs improves turn on over-
shoot characteristics and current limiting. Special circuitry
has also been added to prevent no load runaway conditions.
The output drive clamping circuit limits overshoot of the
power MOSFET gate drive Independent of supply voltage,
so that it greatly enhance the system reliability.
KA7526
Power Factor Correction Controller
8-DIP
8-SOP
1
1
KA7526
2
Internal Block Diagram
IC Characteristics
Parmaeter
KA7526
UVLO
8/13V
Multiplier Input Range (Vm1)
0 ~ 3.8V
Multiplier Input Range (Vm2)
Vref ~ Verf + 2V
Maximum Current Sense Voltage
1.65V
Pin4 Threshold(Vmo)
K =
+
-
+
-
Vm1
(Vm2-Vref)
2.5V Ref
Internal
Bias
+
-
Timer R
+
-
+
-
8
7
5
6
1
4
3
2
V
CC
36V
UVLO
7.5V
1.8V
Zero Current
Detector
Current Sense
Comparator
Vmo
Vm1
Multiplier
Vm2
Error Amp
GND
EA OUT
Vea(-)
INV
1.8V
+
-
Over Voltage
Protection
OUT
V
CC
S
R
Q
Drive
Output
Vref
Vref
Idet
CS
MULT
240mV
5V
13V
40k
8pF
1.65V
0~3.8V
Vref~Vref+2V
KA7526
3
PIN Assignments
Pin Definitions
Pin Number
Pin Name
Pin Function Descrition
1
INV
Inverting input of the error amplifier. The output of the boost
converter should be resistively divided to 2.5V and con-
nected to this pin.
2
EA OUT
The output of the error amplifier. A feedback compensation
network is placed between this pin and the INV pin
3
MULT
Input to the multiplier stage. The full-wave rectified AC is
divided to less than 3.8V and is connected to this pin.
4
CS
Input to the PWM comparator. The Current is sensed in the boost
stage by a resistor in the source lead of MOSFET. An internal leading
edge blanking circuitry has been included to reject any high
frequency noise present on the current waveform.
5
Idet
The zero current detector senses the inductor current by monitoring
when the boost inductor auxilary winding voltage falls below 1.8V.
6
GND
The ground potential of all the pins.
7
OUT
The output of a high-current power driver capable of driving
the gate of a power MOSFET.
8
V
CC
The logic and control power supply connection.
1
2
3
4
5
6
7
8
INV
EA OUT
MULT
CS
Vcc
OUT
GND
Idet
(Top View)
KA7526
4
Absolute Maximum Ratings
Note :
Based in 8-DIP
Temperature Characteristics (-25
o
C
Ta
125
o
C )
Parameter
Symbol
Value
Unit
Supply voltage
V
CC
30
V
Peak drive output current
I
OH
, I
OI
500
mA
Driver output clamping diodes
V
O
>V
CC
or V
O
<-0.3V
Iclamp
10
mA
Detector clamping diodes
Idet
3
mA
Error amp, multiplier and
comparator input voltage
V
IN
-0.3 to 6
V
Operating temperature range
Topr
-25 to 125
o
C
Storage temperature range
Tstg
-65 to 150
o
C
Power dissipation
(Note)
Pd
0.8
W
Thermal resistance
(Note)
(Junction-to-air)
qja
100
o
C
/W
Parameter
Symbol
Value
Unit
Temperature stability for reference voltage(Vref)
Vref (Typ)
20
mV
Temperature stability for multiplier gain(K)
K/
T (Typ)
-0.2
%/
o
C
KA7526
5
Electrical Characteristics
Unless otherwise specified, for typical values Vcc=12V, Ta=25
o
C, for Min/Max values Ta is the operating ambient temperature range
with
-25
o
C
Ta
125
o
C
.
Parameter
Symbol
Condition
Min.
Typ.
Max.
Unit
UNDER VOLTAGE LOCK OUT SECTION
Start Threshold Voltage
Vth (st)
V
CC
Increasing
12
13
14
V
UVLO Hysteresis
HY(st)
-
4
5
6
V
Supply Zener Voltage
Vz
I
CC
=10mA
30
36
-
V
SUPPLY CURRENT SECTION
Start Up Supply Current
Ist
V
CC
<Vth(st)
-
0.3
0.4
mA
Operating Supply Current
I
CC
Output not switching
-
4
8
mA
Dynamic Operating Supply Current
Idcc
50kHz, CI=1nF
-
5
10
mA
ERROR AMPLIFIER SECTION
Voltage Feedback Input Threshold
Vref
Iref=0mA,-
25
o
C
Ta
125
o
C
2.44
-
2.56
V
Line Regulation
Vref1
12V
Vcc
25V
-
0.1
10
mV
Load Regulation
(Note1)
Vref2
0mA
Iref
2mA
-
0.1
10
mV
Temperature Stability of Vref
(Note2)
Vref3
-25
o
C
Ta
125
o
C
-
20
-
mV
Input Bias Current
Ib(ea)
-
-0.5
-
0.5
A
Output Source Current
Isource
Vm2=3V
-2
-4.5
-
mA
Output Sink Current
Isink
Vm2=2V
3
4.5
-
mA
Output Voltage Range
(Note2)
Veao
No Load on E.A Output
1.2
-
5.6
V
Slew Rate
SR
-
-
0.6
-
V/
s
MULTIPLIER SECTION
Input Bias Current (pin3)
Ib(m)
-
-0.5
-
0.5
A
M1 Input Voltage Range (pin3)
Vm1
-
0
-
3.8
V
M2 Input Voltage Range (pin2)
Vm2
-
Vref
-
Vref+2
V
Multiplier Gain
(Note3)
K
Vm1=1V,
Vm2=2.7 to 3.3V
0.49
0.62
0.74
1/V
Maximum Multiplier Output Voltage
Vomax(m) Vea(-)=0V, Vm1=2V
1.55
1.65
1.75
V
Temperature Stability of K
(Note2)
K/
T
-25
o
C
Ta
125
o
C
-
-0.2
-
%/
o
C
KA7526
6
Electrical Characteristics (Continued)
Notes :
1. Because the reference is not brought out externally, this specification cannot be tested on the package part. It is guaranteed
by design.
2. This parameter, although guaranteed, is not tested in production.
3. K =
Parameter
Symbol
Condition
Min.
Typ.
Max. Unit
CURRENT SENSE SECTION
Input Offset Voltage
(Note2)
Vio(cs)
Vm1=0V, Vm2=2.2V
-10
3
10
mV
Input Bias Current
Ib(cs)
0V
V
CC
1.7V
-1
-0.3
1
A
Current Sense Delay to Output
(Note2)
td(cs)
-
-
200
500
ns
DETECT SECTION
Detect Input Threshold
Vth(det)
Vdet Increasing
1.5
1.8
2.1
V
Detect Hysteresis
HY(det)
-
180
240
400
mV
Input Low Clamp Voltage
Vclamp(I)
Idet=-100
A
0.45
0.75
1
V
Input High Clamp Voltage
Vclamp(h)
Idet=3mA
6.7
7.5
8.3
V
Input Bias Current
Ib(det)
1V
Vdet
6V
-1
-0.2
1
A
Input High/low Clamp Diode Current
(Note2)
Iclamp
-
-
-
3
mA
OUTPUT DRIVER SECTION
Output Voltage High
V
OH
I
O
=-10mA, V
CC
=12V
8.5
9
-
V
Output Voltage Low
V
OL
I
O
=10mA, V
CC
=12V
-
0.8
1
V
Rising Time
(Note2)
tr
CI=1nF
-
130
200
ns
Falling Time
(Note2)
tf
CI=1nF
-
50
120
ns
Maximum Output Voltage
Vomax(o)
V
CC
=20V
12
13
15
V
Output Voltage With Uvlo Activated
Vomin(o)
V
CC
=5V, I
O
=100
A
-
-
1
V
RESTART TIMER SECTION
Restart Time Delay
td(rst)
Vm1=1V, Vm2=3.5V
-
300
-
s
OVERVOLTAGE PROTECTION SECTION
Voltage Feedback Input Threshold
Vth(ovp)
Vcs=-0.5V, Vm1=1V
Vdet=0V
1.7
1.8
1.9
V
Pin4 Threshold
Vm1
(Vm2-Vref)
(Vm1=Vpin3, Vm2=Vpin2)
KA7526
7
Typical Performance Characteristics
2.5
3.0
3.5
4.0
4.5
5.0
-0.2
0.0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
Fig1. E.A. Output Voltage vs C.S. Threshold
Vm1=1.5V
Vm1=1V
Vm1=4V
Vm1=0.5V
C
.
S
T
h
r
e
s
hol
d V
o
lt
age [
V
]
EA Output Voltage [V]
0
1
2
3
4
5
-0.2
0.0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
Fig2. Multiplier Input Voltage vs C.S. Threshold
Veao=3.25V
Veao=3V
Veao=2.75V
Veao=5V
Veao=2.5V
C.
S
.
T
h
r
e
s
hold V
o
lt
age [
V
]
Multiplier Input Voltage [V]
0
5
10
15
20
25
30
35
40
45
0.0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
Fig3. Supply Current VS Supply Voltage
Su
p
p
l
y
C
u
rr
e
n
t
[
m
A]
Supply Voltage [v]
-40
-20
0
20
40
60
80
100
120
140
2.45
2.46
2.47
2.48
2.49
2.50
2.51
2.52
2.53
2.54
Fig4. Reference Voltage vs Temperature
R
e
f
e
r
e
nc
e V
o
l
t
a
g
e
(
V
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
12.5
12.6
12.7
12.8
12.9
13.0
13.1
13.2
13.3
13.4
Fig5. Start-up Threshold vs Temperature
S
t
ar
t
-
Up T
h
r
e
s
h
o
l
d
V
o
lt
age
(
V
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
3.5
4.0
4.5
5.0
5.5
6.0
6.5
Fig6. UV Lockout Hysteresis vs Temperature
U
V
Lo
c
k
ou
t
H
y
s
t
e
r
es
i
s
(
V
)
Ambient Temperature (
)
Figure 1. EA Output Voltage vs C.S. Threshold
Figure 2. Multiplier Input Voltage vs C.S. Threshold
Figure 3. Supply Current vs Supply Voltage
Figure 4. Reference Voltage vs Temperature
Figure 5. Start-Up Threshold vs Temperature
Figure 6. UV Lockout Hysteresis vs Temperature
KA7526
8
Typical Performance Characteristics (continued)
-40
-20
0
20
40
60
80
100
120
140
0.00
0.04
0.08
0.12
0.16
0.20
0.24
0.28
0.32
0.36
0.40
Fig7. Start-up Supply Current vs Temperature
S
t
ar
t
-
up S
upply
Cu
r
r
ent
(
m
A
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
-10
-9
-8
-7
-6
-5
-4
-3
-2
Fig8. E.A. Source Current vs Temperature
EA So
u
r
c
e
C
u
rre
n
t
(mA)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
0
1
2
3
4
5
6
7
8
9
10
Fig9. Sink Current vs Temperature
E
A
Si
n
k
C
u
rre
n
t
(mA)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
-0.5
-0.4
-0.3
-0.2
-0.1
0.0
0.1
0.2
0.3
0.4
0.5
Fig.10 Input Bias Current vs Temperature
E
A
I
nput
B
i
as
Cu
r
r
ent
(
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
0.45
0.50
0.55
0.60
0.65
0.70
0.75
Fig.11 Multiplier Gain vs Temperature
M
u
lt
iplier
G
a
in(
1
/
V
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
1.68
1.72
1.76
1.80
1.84
1.88
1.92
Fig.12 Idet Threshold High vs Temperature
I
det
T
h
r
e
s
hold
H
i
gh(
V
)
Ambient Temperature(
)
Figure 7. Start-Up Supply Current vs Temperature
Figure 8. EA Source Current vs Temperature
Figure 9. EA Sink Current vs Temperature
Figure 10. EA Input Bias Current vs Temperature
Figure 11. Multiplier Gain vs Temperature
Figure 12. Idet Threshold Volyage vs Temperature
KA7526
9
Typical Performance Characteristics (continued)
-40
-20
0
20
40
60
80
100
120
140
0
40
80
120
160
200
240
280
320
360
400
Fig.13 Idet Input Hysteresis vs Temperature
I
d
et
I
n
p
u
t
Hy
s
t
er
es
i
s
(m
V
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
0
100
200
300
400
500
600
Fig.14 Restart Time vs Temperature
Re
s
t
a
r
t
T
i
m
e
(
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
1.45
1.50
1.55
1.60
1.65
1.70
1.75
1.80
1.85
Fig.15 Max. Mult. Output Voltage vs Temperature
M
a
x
.
M
u
l
t
i
Ou
tp
u
t
V
o
l
t
a
g
e
(
V
)
Ambient Temperature(
)
-40
-20
0
20
40
60
80
100
120
140
0
1
2
3
4
5
6
7
8
Fig.16 Supply Current vs Temperature
S
upply
Cur
r
ent
(
m
A
)
Ambient Temperature(
)
Figure 13. Idet Input Hysteresis vs Temperature
Figure 14. Restart Time vs Temperature
Figure 15. Max.Mult.Output Voltage vs Temperature
Figure 16. Supply Current vs Temperature
KA7526
10
Operating Description
KA7526 is high performance, critical conduction, current-mode power factor controller specifically designed for use in off-
line active preconverters with minimal external components. This device provides the necessary features which are required to
significantly en-hance poor power factor loads by keeping the ac line current sinusoidal and in phase with the line voltage.
KA7526 contains many of the building blocks and protection features that are employed in modern high performance current
mode power supply controllers. A description of each of the function blocks is given below.
START-UP
An Undervoltage Lockout comparator has been incorporated to guarantee that IC is fully functional before enabling the output
stage. The positive power supply terminal (Vcc) is monitored by the UVLO comparator with the upper threshold set at 13V
and the lower threshold at 8V. In the stand-by mode, with Vcc at 12.5V, the required supply current is less than 0.3mA . This
large hysteresis and low start-up current allow the implementation of efficient bootstrap start-up techniques, making this
device ideally suited for wide range off-line preconverter applications.
Fig.1.1 shows the start-up circuit. Circuit operation is as follows:
The start-up capacitor (Cst) is charged by current through start-up resistor (Rst) minus the start-up current drawn by the IC.
Once the capacitor voltage reaches the start-up threshold, the IC turns on, starting the switching of the MOSFET. The opera-
tion of the IC demands an increase in operating current which results in discharging the capacitor. Before the start-up capacitor
voltage is discharged below hysteresis voltage, the auxiliary winding voltage takes over as the supply voltage as shown in Fig.
1.2.
AC
input
KA7526
Vcc
Out
DVcc
Rst
Cst
+
Fig.1.1 Start-up Circuit
t
Vstart
Cst discharges
Hysteresis
Cst charges
from Rst
Fig.1.2 Start-up Capacitor Voltage
Vcc
KA7526
11
Error Amplifier
An Error Amplifier with access to the inverting input and output is provided. The noninverting input is internally biased at
2.5V and is not pinned out. The output voltage of the power factor converter is typically divided down and monitored by the
inverting input. The error amp output is internally connected to the multiplier and is pinned out for external loop compensa-
tion. Typically, the loopbandwidth is set below 20Hz, so that the amplifer's output voltage is relatively constant over a given ac
line cycle. In effect, the error amp monitors the average output voltage of the converter over several line cycles. Input bias cur-
rent(0.5uA, max) can cause an output voltage error that is equal to the product of the input bias current and the value of the
upper divider resistor, R1 in Fig. 2.1.
Over Voltage Protection
The low bandwidth (typically below 20Hz) characteristic of Error Amplifier control loop results in output voltage runaway
condition. This condition can occur during initial start-up, sudden load removal, or during output arcing. The over voltage
comparator monitors the output voltage of the error amplifier. When load is removed, error amp output swings lower than
1.8V, comparator is triggered high and output driver is turned off till the error amp inverting input voltage drops below 2.5V.
At this point, the error amp output swings positive, turns the output driver back on. .
Multiplier
A single quadrant, two input multiplier is the critical element that enables this device to get power factor correction. One input
of multiplier(Pin 3) is connected to an external resistor divider which monitors the rectified ac line. The other input is inter-
nally driven by a DC voltage which is the difference of error amplifier output (Pin 2) and reference voltage, Vref. The multi-
plier is designed to have an extremely linear transfer curve over a wide dynamic range, 0V to 3.8V for Pin 3, and 2.5V to 4.5V
for error amplifier output under all line and load conditions.
The multiplier output controls the current sense comparator threshold as the ac voltage traverses sinusoidally from zero to
peak line. This allows the inductor peak current to follow the ac line thus forcing the average input current to be sinusoidal. In
other words, this has the effect of forcing the MOSFET on-time to track the input line voltage, resulting in a fixed drive output
on-time, thus making the preconverter load appear to be resistive to the ac line.
The equation below describes the relationship between multiplier output and inputs.
Vmo = K
Vm1
(Vm2-Vref)
K : Multiplier gain
Vm1: Voltage at Pin 3
Vm2: Error amp output voltage
Vmo: Multiplier output voltage
-
+
-
+
x
1
2
INV
EA OUT
1.8V
Vref
Over Voltage
Vref
To Multiplier
To Drive
Output Shutdown
Ccomp
Comparator
R1
R2
R3
Band width= 1/(2
R1
Ccomp)
+
_
Fig.2.1 Error Amp and Over Voltage Comparator
+
KA7526
12
Current Sense Comparator
The current sense comparator adopt the RS latch configuration to ensure that only a single pulse appears at the drive output
during a given cycle. MOSFET drain current is converted to voltage using an external sense resistor in series with the external
power MOSFET. When sense voltage exceeds the threshold set by the multiplier output, the current sense comparator termi-
nates the gate drive to the MOSFET and resets the PWM latch. The latch insures that the output remains in a low state after the
MOSFET drain current falls back to zero.
The peak inductor current under normal operating conditions is controlled by the multiplier output, Vmo.
Abnormal operating conditions occur during preconverter start-up at extremely high line or as output voltage sensing is lost.
Under these conditions, the multiplier output and current sense threshold will be internally clamped to 1.65V. Therefore, the
maximum peak switch current is limited to:
Ipk(max) = 1.65V / Rsense
An internal R/C filter has been included to attenuate any high frequency noise that may be present on the current waveform.
This circuit block eliminates the need for an external R/C filter otherwise required for proper operation of the circuit.
+
-
+
-
+
+
Vref
2
3
1.65V
Current Sense
Comparator
Error Amp
.
Vmo
Vm1
Vm2
INV
MULT
EA OUT
+
-
1
Fig.3.1 Multiplier Block
4
CS
4
cs
1.65V
Multiplier
Output
Rsense
can be eliminated
External R/C Filter
Fig. 4.1 Current Sense Circuit
+
-
KA7526
13
Zero Current Detector
KA7526 operates as a critical conduction current mode controller. The power MOSFET is turned on by the zero current detec-
tor and turned off when the peak inductor current reaches the threshold level established by the multiplier output. The slope of
the inductor current is indirectly detected by monitoring the voltage across a separate winding and connecting it to the zero
current detector Pin 5.
Once the inductor current reaches ground level, the voltage across the winding reverses polarity. When the Idet input falls
below 1.8V, the comparator output is triggered to the low state.
To prevent false tripping, 240mV of hysteresis is provided. The zero current detector input is internally protected by two
clamps.
The upper 7.5V clamp prevents input over voltage breakdown while the lower 0.75V clamp prevents substrate injection. An
internal current limit resistor protects the lower clamp transistor in case the Idet pin is accidently shorted to ground.
A watchdog timer function was added to the IC to eliminate the need for an external oscillator when used in stand-alone appli-
cations. The timer provides a means to automatically start or restart the preconverter if the drive output has been off for more
than 300us after the inductor current reaches zero.
Drive Output
The KA7526 contains a single totem-pole output stage specifically designed for direct drive of power MOSFET. The drive
output is capable of up to 500mA peak current with a typical rise and fall time of 130ns, 50ns each with a 1.0nF load. Addi-
tional internal circuitry has been added to keep the drive output in a sinking mode whenever the UVLO is active. This charac-
teristic eliminates the need for an external gate pull-down resistor. Internal voltage clamping ensures that output driver is
always lower than 13V when supply voltage variation exceeds more than rated Vgs threshold (typ 20V) of the external MOS-
FET. This eliminates an external zener diode and extra power dissipation associated with it that otherwise is required for reli-
able circuit operation.
KA7526
14
APPLICATION CIRCUIT #1
< 90 ~ 265V
AC
Input, 400V
DC
, 32W
2 Lamps Self-oscillating Ballast >
D1
D2
D3
D4
C4
R1
R2
R4
V1
L1
C1
C3
C2
Fuse
AC
Input
+
C7
R3
C5
R8
C10
+
C8
C6
6
4
3
8
1
5
7
2
IC 1
R7
D6
R5
R6
L2
D5
R11
Q1
R9
R10
C9
Q2
R13
C11
L6
R14
L5
L5
L3
L4
R17
R18
D7
D8
R16
C13
L5
L7
R15
Q3
C12
C14
C15
Lamp
1
Lamp
2
C16
GND
KA7526
KA7526
15
Component Listing (for Application circuit #1)
Reference
Value
Part Number
Manufacturer
R1, 2
1.2M
-F, 1/4W
26mm Type
-
R3
11k
-F, 1/4W
26mm Type
-
R4
150k
, 1/2W
26mm Type
-
R5
22k
-J, 1/4W
26mm Type
-
R6, 13, 15
47
-J, 1/4W
26mm Type
-
R7
3.3
, 1/4W
26mm Type
-
R8
1
-J, 1W
26mm Type
-
R9
180k
-F, 1/4W
26mm Type
-
R10
820k
-F, 1/4W
26mm Type
-
R11
6.8k
-F, 1/4W
26mm Type
-
R12, 17, 18
390k
-J, 1/4W
26mm Type
-
R14, 16
8.2
-J, 1/4W
26mm Type
-
C1
0.15uF, 630V
MEP-CAP
-
C2, 3
2200pF, 3000V
Y-CAP
-
C4
0.22uF, 630V
MPE-CAP
-
C5
22uF, 35V
Electrolytic
-
C6
0.33uF, 25V
Ceramic
-
C7
1000pF, 50V
Ceramic
-
C8
47uF, 450V
Electrolytic
-
C9
4700pF, 630V
PPF-CAP
-
C10
2200pF, 630V
PPF-CAP
-
C11, 12
0.15uF, 63V
MPF-CAP
-
C13
0.1uF, 50V
Ceramic
-
C14, 15
8200pF, 1000V
PP-CAP
-
C16
0.15uF, 630V
MEP-CAP
-
D1, 2, 3, 4, 7
1000V, 1A
IN4007GP
-
D5
1000V, 1.5A
BYV26C
Philips
D6
75V, 150mA
IN4148
-
D8
-
N413N (DIAC)
-
L1
DR 10
12
DIT-010
-
L2
EI 2519
DBT-002
-
L3, 4
EI 2820
DPT-086
-
L5
SB5S 8
3
4
DDT-005
-
L6, 7
10uH
BS24-100K
-
Fuse
-
52NM250V, 3A
-
V1
430V
INR140, 431
-
IC1
-
KA7526
FairChild
Q1
500V, 4.5A
QFP6N50
FairChild
Q2, 3
400V, 5A
KSC5305D
FairChild
KA7526
16
Application Circuit #2
< 90 ~ 265V
AC
Input, 400V
DC
, 32W
2 Lamps External-oscillating Ballast >
8
7
6
5
1
2
3
4
Fuse
L1
C2
AC Input
V1
C1
C4
C3
NTC
D1
D4
D2
D3
C5
R3
R4
C6
R6
R5
Q1
C9
R7
R8
D5
D6
+
+
R1
R2
C8
PFC Output
Full-wave Rectified Output
KA7526
C7
R9
L2
8
7
6
5
1
2
3
4
To PFC Output
C9
+
T1
R10
Q2
Q3
R11
L3
L4
D7
C14
R16
D8
R12
C10
C11 C12
R13
R18
R19
C19
C20
+
C17
C18
C13
R17
C15
R15
R14
Lamp2
Lamp1
R16
To Full-wave
Rectified
Output
KA7541
Z1
KA7526
17
Component Listing (for Application Circuit #2)
Reference
Value
Part Number
Manufacturer
R1
2.2M
-F, 1/4W
26mm Type
-
R2
12k
-F, 1/4W
26mm Type
-
R3, 12
150k
, 1/2W
26mm Type
-
R4
22k
-J, 1/4W
26mm Type
-
R5, 10, 11
47
-J, 1/4W
26mm Type
-
R6
3.3
, 1/4W
26mm Type
-
R7
1
-J, 1W
26mm Type
-
R8
1.2M
-F, 1/4W
26mm Type
-
R9
10k
Variable Resistor
-
-
R13
22k
-F, 1/4W
26mm Type
-
R14
180k
-J, 1/4W
26mm Type
-
R15, 16
330k
-J, 1/4W
26mm Type
-
R17, 18
680k
-J, 1/4W
26mm Type
-
R19
8.2k
-J, 1/4W
26mm Type
-
C1, 2
0.15uF, 630V
MEP-CAP
-
C3, 4
2200pF, 3000V
Y-CAP
-
C5
0.1uF, 400V
MPE-CAP
-
C6
22uF, 35V
Electrolytic
-
C7
0.33uF, 25V
MPE-CAP
-
C8
0.01uF, 25V
MPE-CAP
-
C9
47uF, 450V
Electrolytic
-
C10
47uF, 35V
Electrolytic
-
C11
0.22uF, 25V
MPE-CAP
-
C12
180pF, 25V
Ceramic
-
C13
0.1uF, 25V
MPE-CAP
-
C14
1000pF, 630V
MPE-CAP
-
C15, 16
4700pF, 1000V
MPE-CAP
-
C17, 18, 19, 20
6800pF, 630V
MPE-CAP
-
D1, 2, 3, 4
1000V, 1A
1N4007
-
D5
FRD(25nS)
BYV26C
Philips
D6
75V, 150mA
1N4148
-
D7,8
1000V, 1.5A
1N4937
-
L1
80mH
BSF2125
-
L2
1.2mH (100T: 7T)
Litz Wire or USTC
EI2820
-
L3, 4
3.1mH
Litz Wire or USTC
EI2820
-
T1
1.2mH(35T:24T:24T)
EE1614
-
Fuse
-
52NM250V, 3A
-
V1
430V
INR140, 431
-
Q1, 2, 3
500V, 6A
SKP6N50
FairChild
Z1
15V, 1W
-
-
KA7526
18
Mechanical Dimensions
Package
Dimensions in millimeters
6.40
0.20
3.30
0.30
0.130
0.012
3.40
0.20
0.134
0.008
#1
#4
#5
#8
0.252
0.008
9.20
0.20
0.79
2.54
0.100
0.031
()
0.46
0.10
0.018
0.004
0.060
0.004
1.524
0.10
0.362
0.008
9.60
0.378
MAX
5.08
0.200
0.33
0.013
7.62
0~15
0.300
MAX
MIN
0.25
+0.10
0.05
0.010
+0.004
0.002
8-DIP
KA7526
19
Mechanical Dimensions
(Continued)
Package
Dimensions in millimeters
4.92
0.20
0.194
0.008
0.41
0.10
0.016
0.004
1.27
0.050
5.72
0.225
1.55
0.20
0.061
0.008
0.1~0.25
0.004~0.001
6.00
0.30
0.236
0.012
3.95
0.20
0.156
0.008
0.50
0.20
0.020
0.008
5.13
0.202
MAX
#1
#4
#5
0~8
#8
0.56
0.022
()
1.80
0.071
MAX0.10
MAX0.004
MAX
MIN
+
0.10
-0.05
0.15
+
0.004
-0.002
0.006
8-SOP
KA7526
20
Ordering Information
Product Number
Package
Operating Temperature
KA7526
8-DIP
-25 ~ +125
o
C
KA7526D
8-SOP
KA7526
21
KA7526
9/25/00 0.0m 001
Stock#DSxxxxxxxx
2000 Fairchild Semiconductor International
LIFE SUPPORT POLICY
FAIRCHILD'S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES
OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF FAIRCHILD SEMICONDUCTOR
INTERNATIONAL. As used herein:
1. Life support devices or systems are devices or systems
which, (a) are intended for surgical implant into the body,
or (b) support or sustain life, and (c) whose failure to
perform when properly used in accordance with
instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of the
user.
2. A critical component in any component of a life support
device or system whose failure to perform can be
reasonably expected to cause the failure of the life support
device or system, or to affect its safety or effectiveness.
www.fairchildsemi.com
DISCLAIMER
FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO ANY
PRODUCTS HEREIN TO IMPROVE RELIABILITY, FUNCTION OR DESIGN. FAIRCHILD DOES NOT ASSUME ANY
LIABILITY ARISING OUT OF THE APPLICATION OR USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HEREIN; NEITHER
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